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JPS6082000

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DESCRIPTION JPS6082000
[0001]
TECHNICAL FIELD The present invention relates to an apparatus for reducing or increasing the
non-linear distortion of an actuator that converts an electrical signal input to a mechanical
vibration output. In particular, when such a gaactivator is a so-called lautsby force, the first two
in the bass range of the speaker. The present invention relates to a distortion synthesizer that
reduces third harmonic distortion and the like. [Technical Background] A representative example
of an actuator for which it is desired that the mechanical vibration output be accurately specified
to the electrical input is, for example, a speaker for music reproduction. Such a single force has
considerable non-linearity with respect to the mechanical output (sound pressure) to the
electrical input regardless of the type of operation principle such as electrostatic type or
electromagnetic type. Due to this non-linearity, higher order harmonic distortion is included in
the output sound pressure from a single force. The main components of this higher harmonic
distortion include second harmonic distortion (second HD) and third harmonic distortion (third T
(I)). Generally, the higher the output sound pressure of the speaker and the lower the vibration
frequency, the greater these harmonic distortions. Motional feedback (MFB) is known as a means
to reduce such outer cloth. However, it is extremely difficult to stably apply a large amount of
MFB, and examples of industrial products that have been successfully reduced in distortion by B
have been high. Furthermore, as a special case, it may be required to increase the nonlinear
distortion of the mechanical vibration output with respect to the electrical input, or d: to change
its distortion component. An example of an actuator that can meet such a requirement is an
instrument speaker. In a conventional electronic musical instrument or the like, a desired
distortion component is added to the fundamental wave component of the electric signal input to
the speaker to distort the sound from the speaker, and the nonlinear distortion of the speaker
itself is electrically controlled. As far as the applicant knows, the idea of making a sound was
conventionally h. [Purpose] The object of the present invention is to provide a stone strain
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synthesizing apparatus capable of reducing, increasing or changing non-linear strain of an
electric / mechanical vibration converting actuator such as a speaker by electrical treatment.
[Summary] In order to achieve the above object, in the present invention, for example, 30 Hz to
15 kT (45 out of non-linear distortion of sound pressure generated by a single force responsive
to an electrical signal input of z Consider the case of canceling the second order HD for the ˜ 90
Hz fundamental and the third order HD for the 30-60 Hz fundamental. First, a signal component
of 90 to 180 Hz is extracted by a filter from an input signal of 30 T (z to 15 ′ ′ k ′ Hz).
Next, this extracted signal component is divided into 1/2 and 1/3, and converted to a 45-90 Hz
signal and a 30-601 Hz signal. In this case, a part of the input signal (301 (z to 15 kHz) (90 to
180) (z) is the second harmonic component for the 1/2 divided signal (45 to 90 Hz) And for the
1/3 frequency divided signal (30 to 60 T (z), it corresponds to the third harmonic component).
The second-order HD generated by the speaker when a 1/2 frequency-divided signal (45 to 90
Hz) is input is selected by appropriately selecting the amplitude and phase of a part (90 to 1-80)
tz of the input signal. If you enter in, it will be cancelled. In addition, the third HD, which
generates a single force when a 1/3 frequency division signal (30 to 60 Hz) is input,
appropriately selects the amplitude and phase of a part (90 to 180 Hz) of the input signal. It is
possible to cancel it by inputting at one time. In the above example, two low-order harmonic
signals (1/2 and 1/3 frequency division signals) are synthesized from one kind of extraction
signal, and these low-order harmonic signals generate noise. The secondary or tertiary HD is
canceled using a part of the input signal. A slight modification of this perspective of distortion
cancellation, the following 9! 17iできる。 Now, 90 to 180 T (z extracted signal 75S (30 to 60
H 2 1/3 frequency divided signal is produced, this 1/3 frequency divided signal is multiplied by
2 to obtain 60 to 120 Hz signal Make 2 A divided signal). Then, when the 1/3 frequency division
signal (30 to 60 Hz) is input, the secondary HD generated by the speaker is generated using a 27
frequency division signal or a part of the input signal (60 to 12 (Hz) The third HD of this speaker
can be extinguished using the other one (90 to 180 Hz) of the extraction signal or the input
signal. [Advantage of the Invention] The feature of the present invention is that the harmonic
cancellation signal for distortion cancellation is synthesized from the original input signal to the
actuator (speaker etc.), and the phase from the original input signal to lower harmonics is not
required. The signal to be drawn is synthesized, and the harmonic distortion generated by the
actuator by the synthesized low order harmonic component is canceled by the original input
signal component. That is, since the distortion cancellation signal corresponds to the actual input
signal itself, the distortion cancellation signal is input to the actuator, so the actuator outputs an
extra high-order harmonic component that is not included in the original input signal. Absent. In
the present invention, by appropriately selecting one amplitude and phase of the distortion
cancellation signal (a part of the input signal) for the combined low-order harmonic signal No. 4,
the output distortion of the ac chek is increased, The stone is also used to change the
composition of the strain.
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[Example 1] r 'Fig. 1 shows a distortion synthesis apparatus that produces a 45-9 Q I (secondorder T (D cancellation signal for the z signal and third-order un = 30- to 60-Hz signal). An
example is shown. Now, it is assumed that a music signal with a frequency bandwidth of 30 Hz to
15 kHz is obtained from a teso recorder or the like (not shown). This music signal is input to a
bypass filter (HpF,) with a cutoff frequency f0 of about 90 Hz as an input signal Ej and Jo. The
HPF 70 passes frequency components of the input signal E (90 of them) (z to 15 kHz). The
output signal EIO of the HPF 10 is input to the equalizer (EQ) 12. F and Q12 have predetermined
frequency characteristics determined in accordance with the room acoustic characteristics
(frequency characteristics and the like) of the speaker system (actuator) used in combination
with the present device. The output signal E12 of the EQ 12 is input to the phase shifter 1'4. The
phase shifter 14 shifts the phase of the signal E12 appropriately. The output signal E14 of the
phase shifter 14 is input to the coefficient unit 16. The coefficient unit 16 changes the amplitude
of the signal E14 into a coefficient by one minute. This coefficient unit can be composed of an
attenuator or an amplifier. The adder 18 of the coefficient unit 16 adds the signal F and 16 to a
composite signal E4θ described later, and outputs an output signal E. Output This signal E. For
example, it is sent to the speaker system via a power amplifier (not shown). This speaker system
is mainly driven by the synthesized signal E, 40 for signal components of 90 Hz or less, and is
mainly driven by the signal E16 for signal components of 90 Hz to 151 <) Tz. The secondary HD
and the third HD generated by the speaker by the signal E40 of 90 Hz or less are canceled by the
negative phase signal components (90 to 180 T (z)) included in the signal E16 and
corresponding to these HDs. Elements 10-18 receive the input signal E1. An output signal E by
mixing a predetermined portion (90 to 180 Hz) of the second signal with the synthesized signal
E40 with a predetermined amplitude ratio and a predetermined phase relationship. Configuring
the mixing circuit 100 to provide The input signal E7 is input to a noise filter (BPF) z o having a
bandwidth fb of about 90 to 180 Hz. The BPF 20 extracts a predetermined frequency component
(90 to 1.80 Hz) from the input signal Ei and outputs an extraction signal E20. The extraction
signal E20 is input to the zero cross sensor 22. The sensor 22 can be configured by an analog OP
amplifier or the like.
The sensor 22 converts the extraction signal E20 into a rectangular signal E22 whose level is
inverted at the ground potential. This signal TF, 22 is converted by the waveform shaper 24 into
a fast rising / falling, constant amplitude rectangular wave signal F, 24. The shaper 24 can be
configured by a Schmitt circuit or the like. The signal E24 is converted by the 1/2 divider 26 into
a 1/2 divided signal 'fF, 26 having frequency components of 45 to 90 Hz. The distributor 26 can
be constituted by a TW clip flosso or the like. The 1/2 frequency-divided signal E26 (square
wave) is converted by the waveform converter 28 into a sine wave signal E2B of constant
amplitude. There are various possible configurations following this square wave / sine wave
conversion. -For example, force as follows. First, the signal E26 is integrated by a Miller
integrator or the like to convert it into a triangular wave. The triangular wave is converted into a
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digital signal X by a digital converter. This signal X is being input as the address data to the ROM
in which the data corresponding to f (x) = sln x is written. This ROM acts as a code converter that
converts a linear function to a sine function. The sine wave data (digital) read out from this ROM
is converted to a sine wave signal E28 through a D / A converter and an appropriate low-pass 9
filter. The triangular wave may be converted into a sine wave by a tangent approximation method
used by a function generator or the like. The constant amplitude sinusoidal signal F, 2 B is input
to the voltage control amplifier (vCA) 30. A gain control signal E60 having a DC potential
corresponding to or proportional to the amplitude of the extraction signal E2θ is input to the
VCA 30. The VCA 30 amplifies the signal E2B with a gain corresponding to the control signal
E60. That is, the constant amplitude signal E2B is amplitude-modulated by the signal 'fF, 60
corresponding to or proportional to the amplitude of the extraction signal E20. The VCA 30 can
be configured, for example, using the AGC network disclosed in US Patent Publication (USP) No.
3.7 '25,800 (issued April 3, 1973). Thus, a signal E30 having an amplitude component similar to
that of the extraction signal E20 and a half frequency component (45 to 90 Hz) of the extraction
signal E20 is obtained. The details of a technique for synthesizing a lower frequency (45 to 90
Hz) sine wave signal E30 having an amplitude component corresponding to a predetermined
frequency (90 to 180 Hz) sine wave signal E20 in this way are described in Japanese Patent
Application Since it is described in Sho 58-45193 (filed on March 17, 1984), those who are
interested should also refer to this Japanese Patent Application.
The output signal E30 of the VCA 30 is input to the phase shifter 32. The phase shifter 32
appropriately shifts the phase of the signal 'B30. The output signal E 32 f of the phase shifter 32
is applied to the first terminal of the phase inversion switch 34. The signal E32 is still converted
by the phase inverter 36 into the antiphase signal E36. You can reverse jA1 commandments. The
reverse phase signal E36 is applied to the second terminal of the switch 34. The switch 34
selects the signal B32'1 or signal B36 and sends it to the coefficient unit 38. The coefficient unit
38 changes the amplitude 1jq of the input signal (E32 or E36) into a coefficient by 2 minutes.
The output signal E 3 B of the coefficient unit 38 is input to the adder 40. The rectangular wave
signal E24 from the waveform shaper 24 is converted by the 1/3 frequency divider 42 into an IA
frequency-divided signal E42 having frequency components of 30 to 60 H2. The frequency
divider 42 can be constituted by a ternary ring counter or the like. The 1/3 frequency-divided
signal E42 (square wave) is converted by the waveform converter 44 into a constant amplitude
sine wave signal E44. The sine wave signal E44 is input to the vCA 46. The gain control signal
E60 is input to the VCA d6. The VCA 46 has an amplitude component corresponding to the
extraction signal E20, and outputs a signal 1846 of one-third frequency component (30 to 60
TTz) of the extraction signal F220. Waveform converter 44 and VCA 46 may be similar to
waveform converter 28 and VCA 30 described above. The output signal E46 of the VCA 46 is
input to the phase shifter 48. The phase shifter 48 appropriately shifts the phase of the signal
E46. The output signal E4s of the transfer unit 48 (given to the first terminal of the dz phase
inversion switch 50). The signal B4B is also converted into the antiphase signal E52 by the phase
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inverter 52. The inverter 52 may be an analog amplifier having a gain of -1. The reverse phase
signal E52 is applied to the second terminal of the switch 50. The switch 50 is a signal '? , 48 bite
signal E 52 is selected and sent to the coefficient unit 54. The coefficient unit 54 changes the
amplitude of the input signal (848 or E52) into a coefficient by 3 minutes. The output signals F
and 54 of the coefficient unit 54 are input to the adder 40. This adder 40 provides the adder 18
with a synthesized signal E40 corresponding to the sum of the signal BJ8 (45 to 90 Hz) from the
coefficient unit 38 and the signal g54 (30 to 60) (z) from the coefficient unit 54. . Elements 22 to
54 have an amplitude component corresponding to the amplitude of the extraction signal E20
and a composite signal having extraction components' E, and frequency components
corresponding to lower harmonics (here, 1/2 order and 1/3 order) of 20. The synthesis circuit
200 that produces E40 is configured.
The extraction signal E20 from the BPF 20 is input to the phase shifters 56 and 5B. The phase
shift amount of the phase shifter 56 ° 58 is set such that the phase difference between its
output signals E 56 and E 5 B is, for example, approximately 90 °. In this case, the signal E56
becomes As stone ωt, and the signal E5B becomes Acosωt (A indicates amplitude and ω
indicates angular frequency). The signals E56 and E5g are input to the AC / bC converter 60. The
converter outputs a DC signal corresponding to or in proportion to the sum of squares of two
input signals as a gain control signal E60. That is, E6θ−E56 ′ ′ + E5B ′ ′ − = A2sIn2ωt +
A2cos2ωt = A, or F, 60 = E 562 + E 5 g2 ′ = A ′ ′. The signal A or A2 corresponds to only the
amplitude component of the extraction signal g20, and indicates a direct current component
independent of the frequency component. Thus, VCA 3 o 46 is responsible for amplitude
modulating the constant amplitude sinusoidal signal E 28 ° E 44 with a control signal E 60 that
corresponds only to the amplitude component of the extracted signal E 20. The configuration of
the force elements 56 to 60 may be constituted by the vector synthesis circuit control signal
generation circuit as shown in FIGS. 2, 15 and 16 of PCT Application Patent No. Jp / 7810 OO40.
Good. In this configuration (56 to 60), it is also possible to use a normal detection / rectifier
circuit + eliminator circuit (LPF). In FIG. 1, the secondary T (D (90 to 180H2) generated by the
speaker etc. by the signal E38 (45 to 90 Hz) is struck by a part (90 to 180 Hz) of the signal EJ6
(90 to 15 kHz). I hate to erase it. In order to realize the cancellation of the secondary HD, the 1
辰 width of the 90-18011z component in the signal E16 corresponds to the amplitude of the
secondary HD component of the speaker caused by the signal E3B in a one-to-one
correspondence, and It is necessary to adjust the phase of the 90 to 180 Hz component and the
phase of the secondary HD component of the speaker to the opposite phase. Among them, the
amplitude adjustment can be performed by the coefficient units 16 and 38, and the phase
adjustment can be performed by the phase shifters 14 and 32. By the operation of the switch 34,
the distortion canceling operation can be switched to the distortion adding operation. Further,
the distortion component of the sound pressure generated from the single force can be
electrically changed by shifting the wedge width adjustment and the phase adjustment from the
distortion cancellation point. Similarly, 3rd HD cancellation, addition.
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A change can also be made by the operation of the coefficient unit 16.54, the phase shifter 14 °
48 and the switch 50. Incidentally, in the configuration of FIG. 1, even if the element 10 and the
element 16 are omitted and 7 ′ ′ and 1 = B16, practical distortion synthesis equipment can be
obtained. It is of course possible to omit any of the elements 10-16. Also, the HPF 10 may be a
BPF 'with a desired passband width. Alternatively, it may be a band rejection filter (BRF) for
cutting a specific frequency component. [Embodiment 2] FIG. 2 shows an example of a distortion
synthesizing apparatus for producing a secondary HD cancellation signal for a 45 to 90 Hz signal
and a secondary (D cancellation) signal for a 30 to 60 Hz signal. The component of the input
signal 'Ei (30 to 15 kT (z), 60 to 15 k) Tz is input to the adder 18 via the HPF 1θ, EQ 12 °
phase shifter 14 and coefficient unit 16. An extraction signal E20 corresponding to a 90 to 180
Hz component of the input signal Ei is input to the zero cross sensor 22 via the BPF 20. This
signal E20 is converted by the elements 22, 24 26.2B, 3θ, 32, 34, 36.38 + 56.58.60 into a 4590H3 composite signal g3B. These elements (22-6 (11) may be equivalent to the corresponding
elements of FIG. 1). The extraction signal E21 corresponding to the component of 60 to 120 Hz
among the input signal Ei is input to the zero cross sensor 23 via BPF '1. This signal F221 is an
element 2.9, 25.27. 44.46.4B, 50, 52, 54, 55. 59. 61, it is converted to a combined signal E54 of
30 to 60 H2. Elements 23, 25.27.15.59.61 may be configured similarly to element
22.24.26.56.58.60, respectively. Also, elements 44-54 may be equivalent to the corresponding
elements of FIG. The synthesized signal E 3 B (45 to 90 H 2) and the synthesized signal E s 4 (30
to 60 Hz) are added in the adder 40 to form a synthesized signal E 40 (30 to 90 Hz). This signal
E40 is added to the signal EJ6 (60 to 15 k) lz in the adder 18, and the output signal E. (30〜
151c)Tz)となる。 Here, the secondary HD of the loudspeaker due to the signal F, 54 (30
to 60 'Hz) can be canceled out by the 60 to 120 Hz component in the signal EIG.
Adjustment of this cancellation can be performed by element 14 + 16 + 48 + 50.54. The
secondary HD resulting from the signal E3B (45-90T (z)) can be canceled out by the 90-180 Hz
component in the signal EJ6. This cancellation adjustment is an element 14, 16, ...,? 2, 34,. 9 B
allows you to go to the left. Not only to cancel the distortion, but also to change the component
of the distortion or increase the distortion, the elements 14.16, 32, 34, 38.4 B, 50 ° 54 (in some
cases 10, 12, 21.22) To be able to adjust by adjustment). In the configuration of FIG. 2, if the
element 26 ° 27 is dried with a 1-out counter (IAJ divider), it is possible to cancel, change or
increase the Nth-order HD. Actual Example of Alpha .alpha. 3 FIG. 3 shows an example of a
distortion synthesizing apparatus which produces second and third order cancellation signals for
30 to 60 Hz signals. Of the input signal E7 (30 to 15 kHz), 120 to 15 kT (the component of z is I
(PF 10). EQ12. The signal is input to the adder 72 via the phase shifter 14 and the
coefficient unit 16. Of the input signal Ei, the component of 60 to 15 kI (z (or 60 to 120 Hz)) is T
(PF (BPF) 11, EQ13. Phase shifter 15. An extraction signal E2o corresponding to a 90 to 180 Hz
component of the adder input signal E4 is input to the zero cross sensor 22 via the BPF "2θ"
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through the + and coefficient unit 17. This signal E20 is sent to the sensor 22. Via the waveform
shaper 24 and the IA divider 42, it is converted to the IA divided signal E42 (30 to 60 Hz). This
signal E42 is transmitted to the doubler circuit (multi-shiraya) 7o as a doubled signal E7 + 7. It is
converted to (60 to 120 Hz). The doubler circuit 7θ may be a circuit using EXOR or double wave
current as shown in FIGS. 1 and 4 of Japanese Patent Application No. 58-4, 5193. This signal
E70 has the elements 28 * 30 ° 32, 34, 36,. 60 to 120 T (converted to a synthesized signal E3B
of z through 9 B). These elements (28-38) may be equivalent to the corresponding elements of
FIG. The signal is converted into a signal E54 of 30 to 60 j (z in accordance with 1⁄3 frequencydivided signal E42) via elements 44.46.4 B, 50, 52.54. These elements (44 to 54) may also be
equivalent to the corresponding elements in FIG. The adder 72 supplies a signal E72 (60-15 kHz)
of the sum of the output signal E16 (120-15 kHz) of the coefficient unit 16 and the synthesized
signal E38 (60-120 Hz) to the adder 1J, the unit 76.
Further, the adder 74 is a signal E74 (30 to 15 kT (z or z) of the sum of the output signal EI 7 of
the coefficient unit 17 (60 to 120 kHz i is 60 to 120 Hz) and the synthesized signal E 30 to 120
Hz) are applied to the adder 76. Then, from the adder 76, the output signal E corresponding to
the sum of the signal B72 and the signal E74. (30 to 15 k) Tz) is output. As mentioned above, the
present invention can be realized by various embodiments. It is free within the spirit of the
present invention as to which of the above-described embodiment and other embodiments is
adopted to practice the present invention. The present invention can also be used for a cutter
head for recording, a vibrator for vibration test, an ultrasonic transducer used for diagnosis, flaw
detection, etc., as well as a speaker. In addition, the speaker is not limited to the full range type or
the woofer, and can be used as a skoke or tweeter. In particular, when the present invention is
applied to a squawker or tweeter or a full range speaker, it is effective to control distortion by
changing distortion components or applying distortion in addition to cancellation of higher
harmonic distortion. . The distortion synthesizing devices shown in FIGS. 1 to 3 may be unitized,
and a plurality of these distortion synthesizing units may be used in combination (series /
parallel connection). For example, distortion (harmonic component) may be added to the high
frequency band of 4 kHz or more in the unit regarding the low frequency band of 100 Hz or less
in the first unit. Although the present invention is particularly effective for canceling nonlinear
distortion of an actuator, it can be used not only for the actuator, but also for canceling,
increasing or changing distortion of a recording / reproducing system such as a tape recorder
etc. or an electric circuit.
[0002]
Brief description of the drawings
[0003]
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FIG. 1 is a block diagram showing nine components of the distortion synthesizing apparatus
according to one embodiment of the present invention; FIG. 2 is a block diagram showing
another embodiment of the present invention; FIG. 3 is still another embodiment of the present
invention It is a block diagram showing an example.
10.11 ··· Hyogus filter ;, 1-2.13 · · · Equalizer: 14.15, 32.4 B, se ˜ 59 · · · · "phase shifter",
16.17.38.54 · · · Coefficient unit ', Ig, 40, 72, 74. 76 ... Adder; 20. 21 ... Panto filter filter; 22, 23 ...
Zero cross sensor: 94,? 5: waveform shaper: 26.27, 42: frequency divider , 28.44: waveform
converter, 30. 46: voltage control amplifier; 34 ° 50: phase inversion Switch; s6. S2: phase
inverter; + 61: AC off-chip C converter-70: doubled circuit: 100: mixing circuit; 200: synthesis
circuit; Ei: input Signal; Eo output signal ", B20. B21: extracted signal; EJ 8, B 40, E 54910
combined signal: B 60, B 61: gain control signal.
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